By Edmar Camargo
Introducing the applying of box influence Transistors (FET) as frequency multipliers and harmonic oscillators, this article places emphasis on nonlinear thoughts, and contains a minimum quantity of arithmetic and a mixture of concept and experimentation. It goals to aid microwave and millimeter-wave engineers understand the basic thoughts and layout principles of frequency multipliers and harmonic oscillators. The textual content specializes in the recommendations required to generate harmonics and emphasizes circuits. It explores the layout of slim and bandwidth doublers and triplers - either single-ended and balanced configuration. It additionally explains the organization among oscillator conception and frequency multiplier thought in designing harmonic turbines. the $64000 concerns while employing MIC or MMIC applied sciences are mentioned to assist designers choose the simplest procedure for a specific circuit.
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Additional resources for Design of FET frequency multipliers and harmonic oscillators
All the nonidealities are modeled and the results are shown in Figs. 19 for the FDC and TDC, respectively. As shown, the first-order noise shaping of the FDC is destroyed. The nonlinearity of the VCO tuning curve is the bottleneck to achieving high SNR and dominates over the other nonidealities in both quantizers. 1. The theoretical and modeled SNR with nonidealities is shown. The theoretical values closely match the modeled values and have been confirmed with multiple simulations. References 1.
Requirements of a large tuning range may also lead to higher VCO phase noise and tuning nonlinearity . 1) There is also a requirement to have a zero dc offset at the FDC output . This means that there are an equal number of 1’s and 0’s when the VCO frequency is operating at its free running center frequency. For this to occur, the center frequency must be 4Â smaller than the sampling frequency. This becomes important when the VCO-ADC is used in a DS modulator. S. 1007/978-1-4419-9722-7_4, # Springer Science+Business Media, LLC 2011 51 52 4 Further Analyses: FDC vs.
10 . 2 VCO Phase Noise Fig. 8 VCO phase noise: VerilogA model vs. simulated SpectreRF Fig. 9 Modeling 1/f 3 region of phase noise using a filter 39 40 3 Limitations of the VCO-Based Quantizer Fig. 10 Simulated SpectreRF phase noise transfer function H( f ) is derived through the following derivations. 23). 24). 24) Following the block diagram in Fig. 25), where the filtered jitter is denoted as Dtc. 25) Following Fig. 26). 2 VCO Phase Noise 41 Fig. 27). 28). 28) and Fig. 22). The jitter filter is shown in Fig.